LMP2012MAX/NOPB - NATIONAL SEMICONDUCTOR

LMP2011,LMP2012

LMP2011 Single/LMP2012 Dual High Precision, Rail-to-Rail Output

Operational Amplifier

Literature Number: SNOSA71I

July 1, 2008

LMP2011 Single/LMP2012 Dual

High Precision, Rail-to-Rail Output Operational Amplifier

General Description

The LMP201x series are the first members of National's new

LMPTM precision amplifier family. The LMP201X series offers

unprecedented accuracy and stability in space-saving minia-

ture packaging while also being offered at an affordable price.

This device utilizes patented techniques to measure and con-

tinually correct the input offset error voltage. The result is an

amplifier which is ultra stable over time and temperature. It

has excellent CMRR and PSRR ratings, and does not exhibit

the familiar 1/f voltage and current noise increase that

plagues traditional amplifiers. The combination of the LM-

P201X characteristics makes it a good choice for transducer

amplifiers, high gain configurations, ADC buffer amplifiers,

DAC I-V conversion, and any other 2.7V-5V application re-

quiring precision and long term stability.

Other useful benefits of the LMP201X are rail-to-rail output, a

low supply current of 930 µA, and wide gain-bandwidth prod-

uct of 3 MHz. These extremely versatile features found in the

LMP201X provide high performance and ease of use.

Features

(For VS = 5V, Typical unless otherwise noted)

■Low guaranteed VOS over temperature 60 µV

■Low noise with no 1/f 35nV/√Hz

■High CMRR 130 dB

■High PSRR 120 dB

■High AVOL 130 dB

■Wide gain-bandwidth product 3MHz

■High slew rate 4V/µs

■Low supply current 930µA

■Rail-to-rail output 30mV

■No external capacitors required

Applications

■Precision instrumentation amplifiers

■Thermocouple amplifiers

■Strain gauge bridge amplifier

Connection Diagrams

5-Pin SOT23

20071502

Top View

8-Pin SOIC

20071542

Top View

8-Pin MSOP

20071538

Top View

Ordering Information

Package Part Number Temperature

Range

Package Marking Transport Media NSC Drawing

5-Pin SOT23 LMP2011MF

−40°C to 125°C

AN1A 1k Units Tape and Reel MF05A

LMP2011MFX 3k Units Tape and Reel

8-Pin MSOP LMP2012MM AP1A 1k Units Tape and Reel MUA08A

LMP2012MMX 3.5k Units Tape and Reel

8-Pin SOIC

LMP2011MA LMP2011MA 95 Units/Rail

M08A

LMP2011MAX 2.5k Units Tape and Reel

LMP2012MA LMP2012MA 95 Units/Rail

LMP2012MAX 2.5k Units Tape and Reel

LMP2011 Single/LMP2012 Dual High Precision, Rail-to-Rail Output Operational Amplifier

Absolute Maximum Ratings (Note 1)

If Military/Aerospace specified devices are required,

please contact the National Semiconductor Sales Office/

Distributors for availability and specifications.

ESD Tolerance

Human Body Model 2000V

Machine Model 200V

Supply Voltage 5.8V

Common-Mode Input Voltage −0.3 ≤ VCM ≤ VCC +0.3V

Lead Temperature (soldering

10 sec.) +300°C

Differential Input Voltage ±Supply Voltage

Current at Input Pin 30 mA

Current at Output Pin 30 mA

Current at Power Supply Pin 50 mA

Operating Ratings (Note 1)

Supply Voltage 2.7V to 5.25V

Storage Temperature Range −65°C to 150°C

Operating Temperature Range −40°C to 125°C

2.7V DC Electrical Characteristics Unless otherwise specified, all limits guaranteed for TJ = 25°C,

V+ = 2.7V, V− = 0V, V CM = 1.35V, VO = 1.35V and RL > 1 MΩ. Boldface limits apply at the temperature extremes.

Symbol Parameter Conditions Min

(Note 3)

Typ

(Note 2)

Max

(Note 3)

Units

VOS Input Offset Voltage

(LMP2011 only)

0.8 25

60 μV

Input Offset Voltage

(LMP2012 only)

0.8 36

Offset Calibration Time 0.5 10

TCVOS Input Offset Voltage 0.015 μV/°C

Long-Term Offset Drift 0.006 μV/month

Lifetime VOS Drift 2.5 μV

IIN Input Current -3 pA

IOS Input Offset Current 6 pA

RIND Input Differential Resistance 9 MΩ

CMRR Common Mode Rejection Ratio −0.3 ≤ VCM ≤ 0.9V

0 ≤ VCM ≤ 0.9V

130 dB

PSRR Power Supply Rejection Ratio 95

120 dB

AVOL Open Loop Voltage Gain RL = 10 kΩ95

130

RL = 2 kΩ90

124

VOOutput Swing

(LMP2011 only)

RL = 10 kΩ to 1.35V

VIN(diff) = ±0.5V

2.665

2.655

2.68

0.033 0.060

0.075

RL = 2 kΩ to 1.35V

VIN(diff) = ±0.5V

2.630

2.615

2.65

0.061 0.085

0.105

Output Swing

(LMP2012 only)

RL = 10 kΩ to 1.35V

VIN(diff) = ±0.5V

2.64

2.63

2.68

0.033 0.060

0.075

RL = 2 kΩ to 1.35V

VIN(diff) = ±0.5V

2.615

2.6

2.65

0.061 0.085

0.105

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LMP2011 Single/LMP2012 Dual

Symbol Parameter Conditions Min

(Note 3)

Typ

(Note 2)

Max

(Note 3)

Units

IOOutput Current Sourcing, VO = 0V

VIN(diff) = ±0.5V

Sinking, VO = 5V

VIN(diff) = ±0.5V

ISSupply Current per Channel 0.919 1.20

1.50

2.7V AC Electrical Characteristics TJ = 25°C, V+ = 2.7V, V− = 0V, VCM = 1.35V, VO = 1.35V, and RL > 1

MΩ. Boldface limits apply at the temperature extremes.

Symbol Parameter Conditions Min

(Note 3)

Typ

(Note 2)

Max

(Note 3)

Units

GBW Gain-Bandwidth Product 3 MHz

SR Slew Rate 4 V/μs

θ m Phase Margin 60 Deg

GmGain Margin −14 dB

enInput-Referred Voltage Noise 35 nV/

inInput-Referred Current Noise pA/

enp-p Input-Referred Voltage Noise RS = 100Ω, DC to 10 Hz 850 nVpp

trec Input Overload Recovery Time 50 ms

5V DC Electrical Characteristics Unless otherwise specified, all limits guaranteed for TJ = 25°C, V+ = 5V,

V− = 0V, V CM = 2.5V, VO = 2.5V and RL > 1MΩ. Boldface limits apply at the temperature extremes.

Symbol Parameter Conditions Min

(Note 3)

Typ

(Note 2)

Max

(Note 3)

Units

VOS Input Offset Voltage

(LMP2011 only)

0.12 25

60 μV

Input Offset Voltage

(LMP2012 only)

0.12 36

Offset Calibration Time 0.5 10

TCVOS Input Offset Voltage 0.015 μV/°C

Long-Term Offset Drift 0.006 μV/month

Lifetime VOS Drift 2.5 μV

IIN Input Current -3 pA

IOS Input Offset Current 6 pA

RIND Input Differential Resistance 9 MΩ

CMRR Common Mode Rejection Ratio −0.3 ≤ VCM ≤ 3.2

0 ≤ VCM ≤ 3.2

100

130 dB

PSRR Power Supply Rejection Ratio 95

120 dB

AVOL Open Loop Voltage Gain RL = 10 kΩ105

100

130

RL = 2 kΩ95

132

3 www.national.com

LMP2011 Single/LMP2012 Dual

Symbol Parameter Conditions Min

(Note 3)

Typ

(Note 2)

Max

(Note 3)

Units

VOOutput Swing

(LMP2011 only)

RL = 10 kΩ to 2.5V

VIN(diff) = ±0.5V

4.96

4.95

4.978

0.040 0.070

0.085

RL = 2 kΩ to 2.5V

VIN(diff) = ±0.5V

4.895

4.875

4.919

0.091 0.115

0.140

Output Swing

(LMP2012 only)

RL = 10 kΩ to 2.5V

VIN(diff) = ±0.5V

4.92

4.91

4.978

0.040 0.080

0.095

RL = 2 kΩ to 2.5V

VIN(diff) = ±0.5V

4.875

4.855

4.919

0.0.91 0.125

0.150

IOOutput Current Sourcing, VO = 0V

VIN(diff) = ±0.5V

Sinking, VO = 5V

V IN(diff) = ±0.5V

ISSupply Current per Channel 0.930 1.20

1.50

5V AC Electrical Characteristics TJ = 25°C, V+ = 5V, V− = 0V, VCM = 2.5V, VO = 2.5V, and RL > 1MΩ.

Boldface limits apply at the temperature extremes.

Symbol Parameter Conditions Min

(Note 3)

Typ

(Note 2)

Max

(Note 3)

Units

GBW Gain-Bandwidth Product 3 MHz

SR Slew Rate 4 V/μs

θ m Phase Margin 60 deg

GmGain Margin −15 dB

enInput-Referred Voltage Noise 35 nV/

inInput-Referred Current Noise pA/

enp-p Input-Referred Voltage Noise RS = 100Ω, DC to 10 Hz 850 nVpp

trec Input Overload Recovery Time 50 ms

Note 1: Absolute Maximum Ratings indicate limits beyond which damage may occur. Operating Ratings indicate conditions for which the device is intended to

be functional, but specific performance is not guaranteed. For guaranteed specifications and test conditions, see the Electrical Characteristics.

Note 2: Typical values represent the most likely parametric norm.

Note 3: Limits are 100% production tested at 25°C. Limits over the operating temperature range are guaranteed through correlations using statistical quality

control (SQC) method.

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LMP2011 Single/LMP2012 Dual

Typical Performance Characteristics TA=25C, VS= 5V unless otherwise specified.

Supply Current vs. Supply Voltage

20071555

Offset Voltage vs. Supply Voltage

20071556

Offset Voltage vs. Common Mode

20071557

Offset Voltage vs. Common Mode

20071558

Voltage Noise vs. Frequency

20071504

Input Bias Current vs. Common Mode

20071503

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LMP2011 Single/LMP2012 Dual

PSRR vs. Frequency

20071507

PSRR vs. Frequency

20071506

Output Sourcing @ 2.7V

20071559

Output Sourcing @ 5V

20071560

Output Sinking @ 2.7V

20071561

Output Sinking @ 5V

20071562

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LMP2011 Single/LMP2012 Dual

Max Output Swing vs. Supply Voltage

20071563

Max Output Swing vs. Supply Voltage

20071564

Min Output Swing vs. Supply Voltage

20071565

Min Output Swing vs. Supply Voltage

20071566

CMRR vs. Frequency

20071505

Open Loop Gain and Phase vs. Supply Voltage

20071508

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LMP2011 Single/LMP2012 Dual

Open Loop Gain and Phase vs. RL @ 2.7V

20071509

Open Loop Gain and Phase vs. RL @ 5V

20071510

Open Loop Gain and Phase vs. CL @ 2.7V

20071511

Open Loop Gain and Phase vs. CL @ 5V

20071512

Open Loop Gain and Phase vs. Temperature @ 2.7V

20071536

Open Loop Gain and Phase vs. Temperature @ 5V

20071537

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LMP2011 Single/LMP2012 Dual

THD+N vs. AMPL

20071514

THD+N vs. Frequency

20071513

0.1 Hz − 10 Hz Noise vs. Time

20071515

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LMP2011 Single/LMP2012 Dual

Application Information

THE BENEFITS OF LMP201X

NO 1/f NOISE

Using patented methods, the LMP201X eliminates the 1/f

noise present in other amplifiers. That noise, which increases

as frequency decreases, is a major source of measurement

error in all DC-coupled measurements. Low-frequency noise

appears as a constantly-changing signal in series with any

measurement being made. As a result, even when the mea-

surement is made rapidly, this constantly-changing noise sig-

nal will corrupt the result. The value of this noise signal can

be surprisingly large. For example: If a conventional amplifier

has a flat-band noise level of 10nV/ and a noise corner of

10 Hz, the RMS noise at 0.001 Hz is 1µV/ . This is equiv-

alent to a 0.50 µV peak-to-peak error, in the frequency range

0.001 Hz to 1.0 Hz. In a circuit with a gain of 1000, this pro-

duces a 0.50 mV peak-to-peak output error. This number of

0.001 Hz might appear unreasonably low, but when a data

acquisition system is operating for 17 minutes, it has been on

long enough to include this error. In this same time, the LM-

P201X will only have a 0.21 mV output error. This is smaller

by 2.4 x. Keep in mind that this 1/f error gets even larger at

lower frequencies. At the extreme, many people try to reduce

this error by integrating or taking several samples of the same

signal. This is also doomed to failure because the 1/f nature

of this noise means that taking longer samples just moves the

measurement into lower frequencies where the noise level is

even higher.

The LMP201X eliminates this source of error. The noise level

is constant with frequency so that reducing the bandwidth re-

duces the errors caused by noise.

Another source of error that is rarely mentioned is the error

voltage caused by the inadvertent thermocouples created

when the common "Kovar type" IC package lead materials are

soldered to a copper printed circuit board. These steel-based

leadframe materials can produce over 35 μV/°C when sol-

dered onto a copper trace. This can result in thermocouple

noise that is equal to the LMP201X noise when there is a

temperature difference of only 0.0014°C between the lead

and the board!

For this reason, the lead-frame of the LMP201X is made of

copper. This results in equal and opposite junctions which

cancel this effect. The extremely small size of the SOT-23

package results in the leads being very close together. This

further reduces the probability of temperature differences and

hence decreases thermal noise.

OVERLOAD RECOVERY

The LMP201X recovers from input overload much faster than

most chopper-stabilized op amps. Recovery from driving the

amplifier to 2X the full scale output, only requires about 40

ms. Many chopper-stabilized amplifiers will take from 250 ms

to several seconds to recover from this same overload. This

is because large capacitors are used to store the unadjusted

offset voltage.

20071516

FIGURE 1. Overload Recovery Test

The wide bandwidth of the LMP201X enhances performance

when it is used as an amplifier to drive loads that inject tran-

sients back into the output. ADCs (Analog-to-Digital Convert-

ers) and multiplexers are examples of this type of load. To

simulate this type of load, a pulse generator producing a 1V

peak square wave was connected to the output through a 10

pF capacitor. (Figure 1) The typical time for the output to re-

cover to 1% of the applied pulse is 80 ns. To recover to 0.1%

requires 860ns. This rapid recovery is due to the wide band-

width of the output stage and large total GBW.

NO EXTERNAL CAPACITORS REQUIRED

The LMP201X does not need external capacitors. This elim-

inates the problems caused by capacitor leakage and dielec-

tric absorption, which can cause delays of several seconds

from turn-on until the amplifier's error has settled.

MORE BENEFITS

The LMP201X offers the benefits mentioned above and more.

It has a rail-to-rail output and consumes only 950 µA of supply

current while providing excellent DC and AC electrical per-

formance. In DC performance, the LMP201X achieves 130

dB of CMRR, 120 dB of PSRR and 130 dB of open loop gain.

In AC performance, the LMP201X provides 3 MHz of gain-

bandwidth product and 4 V/µs of slew rate.

HOW THE LMP201X WORKS

The LMP201X uses new, patented techniques to achieve the

high DC accuracy traditionally associated with chopper-sta-

bilized amplifiers without the major drawbacks produced by

chopping. The LMP201X continuously monitors the input off-

set and corrects this error. The conventional chopping pro-

cess produces many mixing products, both sums and

differences, between the chopping frequency and the incom-

ing signal frequency. This mixing causes large amounts of

distortion, particularly when the signal frequency approaches

the chopping frequency. Even without an incoming signal, the

chopper harmonics mix with each other to produce even more

trash. If this sounds unlikely or difficult to understand, look at

the plot (Figure 2), of the output of a typical (MAX432) chop-

per-stabilized op amp. This is the output when there is no

incoming signal, just the amplifier in a gain of -10 with the input

grounded. The chopper is operating at about 150 Hz; the rest

is mixing products. Add an input signal and the noise gets

much worse. Compare this plot with Figure 3 of the LMP201X.

This data was taken under the exact same conditions. The

auto-zero action is visible at about 30 kHz but note the ab-

sence of mixing products at other frequencies. As a result, the

LMP201X has very low distortion of 0.02% and very low mix-

ing products.

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LMP2011 Single/LMP2012 Dual

20071517

FIGURE 2. The Output of a Chopper Stabilized Op Amp

(MAX432)

20071504

FIGURE 3. The Output of the LMP2011/LMP2012

INPUT CURRENTS

The LMP201X's input currents are different than standard

bipolar or CMOS input currents in that it appears as a current

flowing in one input and out the other. Under most operating

conditions, these currents are in the picoamp level and will

have little or no effect in most circuits. These currents tend to

increase slightly when the common-mode voltage is near the

minus supply. (See the typical curves.) At high temperatures

such as 85°C, the input currents become larger, 0.5 nA typi-

cal, and are both positive except when the VCM is near V−. If

operation is expected at low common-mode voltages and

high temperature, do not add resistance in series with the in-

puts to balance the impedances. Doing this can cause an

increase in offset voltage. A small resistance such as 1 kΩ

can provide some protection against very large transients or

overloads, and will not increase the offset significantly.

PRECISION STRAIN-GAUGE AMPLIFIER

This Strain-Gauge amplifier (Figure 4) provides high gain

(1006 or ~60 dB) with very low offset and drift. Using the re-

sistors' tolerances as shown, the worst case CMRR will be

greater than 108 dB. The CMRR is directly related to the re-

sistor mismatch. The rejection of common-mode error, at the

output, is independent of the differential gain, which is set by

R3. The CMRR is further improved, if the resistor ratio match-

ing is improved, by specifying tighter-tolerance resistors, or

by trimming.

20071518

FIGURE 4. Precision Strain Gauge Amplifier

Extending Supply Voltages and Output Swing by Using a

Composite Amplifier Configuration:

In cases where substantially higher output swing is required

with higher supply voltages, arrangements like the ones

shown in Figure 5 and Figure 6 could be used. These config-

urations utilize the excellent DC performance of the LMP201X

while at the same time allow the superior voltage and fre-

quency capabilities of the LM6171 to set the dynamic perfor-

mance of the overall amplifier. For example, it is possible to

achieve ±12V output swing with 300 MHz of overall GBW

(AV = 100) while keeping the worst case output shift due to

VOS less than 4 mV. The LMP201X output voltage is kept at

about mid-point of its overall supply voltage, and its input

common mode voltage range allows the V- terminal to be

grounded in one case (Figure 5, inverting operation) and tied

to a small non-critical negative bias in another (Figure 6, non-

inverting operation). Higher closed-loop gains are also pos-

sible with a corresponding reduction in realizable bandwidth.

Table 1 shows some other closed loop gain possibilities along

with the measured performance in each case.

11 www.national.com

LMP2011 Single/LMP2012 Dual

20071519

FIGURE 5. Composite Amplifier Configuration

TABLE 1. Composite Amplifier Measured Performance

AVR1

(Ω)

(pF)

(MHz)

(V/μs)

en p-p

(mVPP)

50 200 10k 8 3.3 178 37

100 100 10k 10 2.5 174 70

100 1k 100k 0.67 3.1 170 70

500 200 100k 1.75 1.4 96 250

1000 100 100k 2.2 0.98 64 400

In terms of the measured output peak-to-peak noise, the fol-

lowing relationship holds between output noise voltage, en p-

p, for different closed-loop gain, AV, settings, where −3 dB

Bandwidth is BW:

(1)

20071520

FIGURE 6. Composite Amplifier Configuration

It should be kept in mind that in order to minimize the output

noise voltage for a given closed-loop gain setting, one could

minimize the overall bandwidth. As can be seen from Equa-

tion 1 above, the output noise has a square-root relationship

to the Bandwidth.

In the case of the inverting configuration, it is also possible to

increase the input impedance of the overall amplifier, by rais-

ing the value of R1, without having to increase the feed-back

resistor, R2, to impractical values, by utilizing a "Tee" network

as feedback. See the LMC6442 data sheet (Application Notes

section) for more details on this.

20071521

FIGURE 7. AC Coupled ADC Driver

LMP201X AS ADC INPUT AMPLIFIER

The LMP201X is a great choice for an amplifier stage imme-

diately before the input of an ADC (Analog-to-Digital Con-

verter), whether AC or DC coupled. See Figure 7 and Figure

8. This is because of the following important characteristics:

A) Very low offset voltage and offset voltage drift over time

and temperature allow a high closed-loop gain setting

without introducing any short-term or long-term errors.

For example, when set to a closed-loop gain of 100 as the

analog input amplifier for a 12-bit A/D converter, the over-

all conversion error over full operation temperature and

30 years life of the part (operating at 50°C) would be less

than 5 LSBs.

B) Fast large-signal settling time to 0.01% of final value (1.4

μs) allows 12 bit accuracy at 100 KHZ or more sampling

rate.

C) No flicker (1/f) noise means unsurpassed data accuracy

over any measurement period of time, no matter how

long. Consider the following op amp performance, based

on a typical low-noise, high-performance commercially-

available device, for comparison:

Op amp flatband noise = 8nV/

1/f corner frequency = 100 Hz

AV = 2000

Measurement time = 100 sec

Bandwidth = 2 Hz

This example will result in about 2.2 mVPP (1.9 LSB) of

output noise contribution due to the op amp alone, com-

pared to about 594 μVPP (less than 0.5 LSB) when that

op amp is replaced with the LMP201X which has no 1/f

contribution. If the measurement time is increased from

100 seconds to 1 hour, the improvement realized by using

the LMP201X would be a factor of about 4.8 times (2.86

mVPP compared to 596 μV when LMP201X is used) main-

ly because the LMP201X accuracy is not compromised

by increasing the observation time.

D) Copper leadframe construction minimizes any thermo-

couple effects which would degrade low level/high gain

www.national.com 12

LMP2011 Single/LMP2012 Dual

data conversion application accuracy (see discussion un-

der "The Benefits of the LMP201X" section above).

E) Rail-to-Rail output swing maximizes the ADC dynamic

range in 5-Volt single-supply converter applications. Be-

low are some typical block diagrams showing the LM-

P201X used as an ADC amplifier (Figure 7 and Figure

8).

20071522

FIGURE 8. DC Coupled ADC Driver

13 www.national.com

LMP2011 Single/LMP2012 Dual

Physical Dimensions inches (millimeters) unless otherwise noted

5-Pin SOT23

NS Package Number MF0A5

8-Pin MSOP

NS Package Number MUA08A

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LMP2011 Single/LMP2012 Dual

8-Pin SOIC

NS Package Number M08A

15 www.national.com

LMP2011 Single/LMP2012 Dual

Notes

LMP2011 Single/LMP2012 Dual High Precision, Rail-to-Rail Output Operational Amplifier

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